Biased phase sweep transmit diversity

ABSTRACT

Disclosed is a method and apparatus of transmit diversity that is backward compatible and does not significantly degrade performance in additive white guassan noise (AWGN) conditions using a transmission architecture that incorporates a form of phase sweep transmit diversity (PSTD) referred to herein as biased PSTD. Biased PSTD involves transmitting a signal and a frequency swept version of the same signal over diversity antennas at different power levels. By transmitting the two signals at different power levels, the depths of nulls normally seen in AWGN conditions when PSTD is utilized is reduced and performance degradation in AWGN conditions is mitigated.

RELATED APPLICATION

Related subject matter is disclosed in the following applications filed concurrently and assigned to the same assignee hereof: U.S. patent application Ser. No. 09/918,391 entitled, “Space Time Spreading and Phase Sweep Transmit Diversity,” inventors Roger Benning, R. Michael Buehrer, Robert Atmaram Soni and Paul A Polakos; U.S. patent application Ser. No. 09/918,392 entitled, “Symmetric Sweep Phase Sweep Transmit Diversity,” inventors Roger Benning, R. Michael Buebrer, Paul A Polakos and Mark Kraml; U.S. patent application Ser. No. 09/918,086 entitled, “Split Shift Phase Sweep Transmit Diversity,” inventors Roger Benning, R. Michael Buehrer, Robert Atmaram Soni and Paul A Polakos.

BACKGROUND OF THE RELATED ART

Performance of wireless communication systems is directly related to signal strength statistics of received signals. Third generation wireless communication systems utilize transmit diversity techniques for downlink transmissions (i.e., communication link from a base station to a mobile-station) in order to improve received signal strength statistics and, thus, performance. Two such transmit diversity techniques are space time spreading (STS) and phase sweep transmit diversity (PSTD).

FIG. 1 depicts a wireless communication system 10 employing STS. Wireless communication system 10 comprises at least one base station 12 having two antenna elements 14-1 and 14-2, wherein antenna elements 14-1 and 14-2 are spaced far apart for achieving transmit diversity. Base station 12 receives a signal S for transmitting to mobile-station 16. Signal S is alternately divided into signals s_(e) and s_(o), wherein signal s_(e) comprises even data bits and signal s_(o) comprises odd data bits. Signals s_(e) and s_(o) are processed to produce signals S¹⁴⁻¹ and S¹⁴⁻². Specifically, s_(e) is multiplied with Walsh code w₁ to produce signal s_(e)w₁; a conjugate of signal s_(o) is multiplied with Walsh code w₂ to produce signal s_(o)*w₂; signal s_(o) is multiplied with Walsh code w₁ to produce s_(o)w₁; and a conjugate of signal s_(e) is multiplied with Walsh code w₂ to produce s_(e)*w₂. Signal s_(e)w₁ is added to signal s_(o)*w₂ to produce signal S¹⁴⁻¹ (i.e., S¹⁴⁻¹=s_(e)w₁+s_(o)*w₂) and signal s_(e)*w₂ is subtracted from signal s_(o)w₁ to produce signal S¹⁴⁻² (i.e., S¹⁴⁻²=s_(o)w₁−s_(e)*w₂). Signals S¹⁴⁻¹ and S¹⁴⁻² are transmitted at substantially equal or identical power levels over antenna elements 14-1 and 14-2, respectively. For purposes of this application, power levels are “substantially equal” or “identical” when the power levels are within 1% of each other.

Mobile-station 16 receives signal R comprising γ₁(S¹⁴⁻²)+γ₂(S¹⁴⁻²), wherein γ₁ and γ₂ are distortion factor coefficients associated with the transmission of signals S¹⁴⁻¹ and S¹⁴⁻² from antenna elements 14-1 and 14-2 to mobile-station 16, respectively. Distortion factor coefficients γ₁ and γ₂ can be estimated using pilot signals, as is well-known in the art. Mobile-station 16 decodes signal R with Walsh codes w₁ and w₂ to respectively produce outputs: W ₁=γ₁ s _(e)+γ₂ s _(o)  equation 1 W ₂=γ₁ s _(o)*−γ₂ s _(e)*  equation 1a Using the following equations, estimates of signals s_(e) and s_(o), i.e., Ŝ_(e) and Ŝ_(o), may be obtained: Ŝ _(e)=γ₁ *W ₁−γ₂ W* ₂ =s _(e)(|γ₁|²+|γ₂|²)+noise  equation 2 Ŝ _(o)=γ₂ *W ₁+γ₁ W ₂ *=s _(o)(|γ₁|²+|γ₂|²)+noise  equation 2a

However, STS is a transmit diversity technique that is not backward compatible from the perspective of the mobile-station. That is, mobile-station 16 is required to have the necessary hardware and/or software to decode signal R. Mobile-stations without such hardware and/or software, such as pre-third generation mobile-stations, would be incapable of decoding signal R.

By contrast, phase sweep transmit diversity (PSTD) is backward compatible from the perspective of the mobile-station. FIG. 2 depicts a wireless communication system 20 employing PSTD. Wireless communication system 20 comprises at least one base station 22 having two antenna elements 24-1 and 24-2, wherein antenna elements 24-1 and 24-2 are spaced far apart for achieving transmit diversity. Base station 22 receives a signal S for transmitting to mobile-station 26. Signal S is evenly power split into signals s₁ and s₂ and processed to produce signals S²⁴⁻¹ and S²⁴⁻², where s₁=s₂. Specifically, signal s₁ is multiplied by Walsh code w_(k) to produce S²⁴⁻¹=s₁w_(k), where k represents a particular user or mobile-station. Signal s₂ is multiplied by Walsh code w_(k) and a phase sweep frequency signal e^(J2πf) ^(t) to produce S²⁴⁻², i.e., S²⁴⁻²=s₂w_(k)e^(J2πf) ^(s) ^(t)=s₁w_(k)e^(J2πf) ^(s) ^(t)=S²⁴⁻¹e^(J2πf) ^(s) ^(t), where f_(s) is a phase sweep frequency and t is time. Signals S²⁴⁻¹ and S²⁴⁻² are transmitted at substantially equal power levels over antenna elements 24-1 and 24-2, respectively. Note that the phase sweep signal e^(J2πf) ^(s) ^(t) is being represented in complex baseband notation, i.e., e^(J2πf) ^(s) ^(t)=cos(2πf_(s)t)+j sin(2πf_(s)t). It should be understood that the phase sweep signal may also be applied at an intermediate frequency or a radio frequency.

Mobile-station 26 receives signal R comprising γ₁S²⁴⁻¹+γ₂S²⁴⁻². Simplifying the equation for R results in R=γ ₁ S ²⁴⁻¹+γ₂ S ²⁴⁻¹ e ^(J2πf) ^(s) ^(t)  equation 3 R=S ²⁴⁻¹{γ₁+γ₂ e ^(J2πf) ^(s) ^(t)}  equation 3a R=S ²⁴⁻¹γ_(eq)  equation 3b where γ_(eq) is an equivalent channel seen by mobile-station 26. Distortion factor coefficient γ_(eq) can be estimated using pilot signals and used, along with equation 3b, to obtain estimates of signal s₁ and/or s₂.

In slow fading channel conditions, PSTD improves performance (relative to when no transmit diversity technique is used) by making the received signal strength statistics associated with a slow fading channel at the receiver look like those associated with a fast fading channel. However, in additive white gaussan noise (AWGN) conditions, PSTD can significantly degrade performance. Accordingly, there exists a need for a transmit diversity technique that is backward compatible without significantly degrading performance in AGWN conditions.

SUMMARY OF THE INVENTION

The present invention is a method and apparatus of transmit diversity that is backward compatible and does not significantly degrade performance in additive white guassan noise (AWGN) conditions using a transmission architecture that incorporates a form of phase sweep transmit diversity (PSTD) referred to herein as biased PSTD. Biased PSTD involves transmitting a signal and a frequency swept version of the same signal over diversity antennas at different power levels. By transmitting the two signals at different power levels, the depths of nulls normally seen in AWGN conditions when PSTD is utilized is reduced and performance degradation in AWGN conditions is mitigated.

BRIEF DESCRIPTION OF THE DRAWINGS

The features, aspects, and advantages of the present invention will become better understood with regard to the following description, appended claims, and accompanying drawings where

FIG. 1 depicts a wireless communication system employing space time spreading techniques in accordance with the prior art;

FIG. 2 depicts a wireless communication system employing phase sweep transmit diversity in accordance with the prior art; and

FIG. 3 depicts a base station employing code division multiple access (CDMA) and a form of phase sweep transmit diversity (PSTD) referred to herein as biased PSTD in accordance with the present invention.

DETAILED DESCRIPTION

FIG. 3 depicts a base station 30 employing code division multiple access (CDMA) and a form of phase sweep transmit diversity (PSTD) referred to herein as biased PSTD in accordance with the present invention. Biased PSTD involves transmitting a signal and a frequency swept version of the same signal over diversity antennas at different power levels to reduce the depths of nulls. Advantageously, biased PSTD is backwards compatible from the perspective of mobile-stations and does not degrade performance as much as PSTD in additive white gaussan noise (AWGN) conditions. CDMA is well-known in the art.

Base station 30 provides wireless communication services to mobile-stations, not shown, in its associated geographical coverage area or cell, wherein the cell is divided into three sectors α, β, γ. Base station 30 includes a transmission architecture that biased PSTD, as will be described herein.

Base station 30 comprises a processor 32, a splitter 34, multipliers 36, 38, amplifiers 44, 46, and a pair of diversity antennas 48, 50. Note that base station 30 also includes configurations of splitters, multipliers, amplifiers and antennas for sectors β, γ that are identical to those for sector a. For simplicity sake, the configurations for sectors β, γ are not shown. Additionally, for discussion purposes, it is assumed that signals S_(k) are intended for mobile-stations k located in sector α and, thus, the present invention will be described with reference to signals S_(k) being processed for transmission over sector α.

Processor 32 includes software for processing signals S_(k) in accordance with well-known CDMA techniques to produce an output signal S_(k−1). Note that, in another embodiment, processor 32 is operable to process signals S_(k) in accordance with a multiple access technique other than CDMA, such as time or frequency division multiple access.

Signal S_(k−1) is split by splitter 34 into signals S_(k−1)(a), S_(k−1)(b) and processed along paths A and B, respectively, by multipliers 36, 38, and amplifiers 44, 46 in accordance with bias PSTD techniques, wherein signal S_(k−1)(a) is identical to signal S_(k−1)(b) in terms of data. In one embodiment, signal S_(k), is unevenly power split by splitter 34 such that the power level of signal S_(k−1)(a) is higher than the power level of signal S_(k−1)(b). For example, signal S_(k−1) is power split such that signal S_(k−1)(a) gets 5/8 of signal S_(k−1)'s power and signal S_(k−1)(b) gets 3/8 of signal S_(k−1)'s power, i.e., S_(k−1)(a)=√{square root over (⅝)}(S_(k−1)) and S_(k−1)(b)=√{square root over (⅜)}(S_(k−1)). In another example, signal S_(k−1) is power split such that signal S_(k−1)(a) gets ⅔ of signal S_(k−1)'s power and signal S_(k−1)(b) gets ⅓ of signal S_(k−1)'s power. In one embodiment, signal S_(k−1) is unevenly power split by splitter 34 such that the power level of signal S_(k−1)(b) is higher than the power level of signal S_(k−1)(a), or signal S_(k−1) is evenly power split into signals S_(k−1)(a), S_(k−1)(b). Signal S_(k−1)(a) and carrier signal e^(J2πf) ^(c) ^(t) are provided as inputs into multiplier 36 to produce signal S₃₆, where S₃₆=S_(k−1)(a)e^(J2πf) ^(c) ^(t), e^(J2πf) ^(c) ^(t)=cos(2πf_(c)t)+j sin(2πf_(c)t), f_(c) represents a carrier frequency and t represents time.

Signal S_(k−1)(b), phase sweep frequency signal e^(JΘ) ^(s) ^((t)) and carrier signal e^(J2πf) ^(c) ^(t) are provided as inputs into multiplier 38 where signal S_(k−1)(b) is frequency phase swept with signal e^(jΘ) ^(s) ^((t)) and modulated onto carrier signal e^(J2πf) ^(c) ^(t) to produce signal S₃₈=S_(k−1)(b)e^(J2πf) ^(c) ^(t)e^(JΘ) ^(s) ^((t)), wherein Θ_(s)=2πf_(s)t, e^(JΘ) ^(s) ^((t))=cos(2πf_(s)t)+j sin(2πf_(s)t) and f_(s) represents a phase sweep frequency.

Signals S₃₆, S₃₈ are amplified by amplifiers 44, 46 to produce signals S₄₄ and S₄₆ for transmission over antennas 48, 50, respectively, where signal S₄₄=A₄₄S_(k−1)(a)e^(J2πf) ^(c) ^(t), S₄₆=A₄₆S_(k−1)(b)e^(J2πf) ^(c) ^(t)e^(JΘ) ^(s) ^((t)), A₄₄ represents the amount of gain associated with amplifier 44 and A₄₆ represents the amount of gain associated with amplifier 46.

In one embodiment, the amounts of gain A₄₄, A₄₆ are equal. In this embodiment, signal S_(k−1) is split by splitter 34 such that the power level of signal S_(k−1)(a) is higher than the power level of signal S_(k−1)(b), or vice-versa, so that differences in power level between signals S₄₄ and S₄₆ are not as large compared to an even power split of signal S_(k−1).

In another embodiment, the amounts of gain A₄₄, A₄₆ are different and related to how splitter 34 power splits signal S_(k−1). For example, the amount of gain A₄₄, A₄₆ applied to signals S₃₆, S₃₈ should be an amount that would cause the power levels of signals S₄₄ and S₄₆ to be approximately equal. For purposes of this application, power levels are “approximately equal” when the power levels are within 10% of each other. In another example, the signal, e.g., S₃₆ or S₃₈, associated with a greater power level is amplified more than the other signal.

In the case where signal s_(α−1) and/or signals S₃₆, S₄₀ are not biased or unevenly split or amplified, STS performance will degrade because signal S₄₄ will be transmitted at approximately ⅓ of the power at which signal S₄₆ will be transmitted. Advantageously, biasing or unevenly splitting signal s_(α−1) and/or biasing or unevenly amplifying signals S₃₆, S₄₀ mitigates this degradation to STS performance relative to the case where neither signal s_(α−1) nor signals S₃₆, S₄₀ are biased or unevenly split or amplified.

Although the present invention has been described in considerable detail with reference to certain embodiments, other versions are possible. Therefore, the spirit and scope of the present invention should not be limited to the description of the embodiments contained herein. 

1. A method of signal transmission comprising the steps of: splitting a signal s₁ into signals s₁(a) and s₁(b), wherein the signal s₁ is split unevenly such that the signal s₁(a) has an associated power level greater than a power level associated with the signal s₁(b); and phase sweeping the signal s₁(b) using a phase sweep frequency signal to produce a phase swept signal s₁(b).
 2. The method of claim 1 comprising the additional steps of: amplifying the signal s₁ (a) to produce an amplified signal s₁(a); and amplifying the phase swept signal s₁(b) to produce an amplified phase swept signal s₁(b).
 3. The method of claim 2, wherein power levels associated with the amplified signal s₁(a) and the amplified phase swept signal s₁(b) are approximately equal.
 4. The method of claim 2, wherein the signal s₁(a) and phase swept signal s₁(b) are amplified an equal amount.
 5. The method of claim 2, wherein the signal s₁(a) is amplified an amount greater than an amount phase swept signal s₁(b) is amplified.
 6. A method of signal transmission comprising the steps of: splitting a signal S₁ into signals s₁(a) and s₁(b), wherein the signal S₁ is split unevenly such that the signal s₁(a) has an associated power level greater than a power level associated with the signal s₁(b); and phase sweeping the signal s₁(a) using a phase sweep frequency signal to produce a phase swept signal s₁(a).
 7. The method of claim 6 comprising the additional steps of: amplifying the signal s₁(b) to produce an amplified signal s₁(b); and amplifying the phase swept signal s₁(a) to produce an amplified phase swept signal s₁(a).
 8. The method of claim 7, wherein power levels associated with the amplified signal s₁(b) and the amplified phase swept signal s₁(a) are approximately equal.
 9. The method of claim 7, wherein the signal s₁(b) and phase swept signal s₁(a) are amplified an equal amount.
 10. The method of claim 7, wherein the signal s₁(b) is amplified an amount greater than an amount phase swept signal s₁(a) is amplified.
 11. A base station comprising: a splitter for splitting a signal s₁ into signals s₁(a) and s₁(b), wherein the signal s₁ is split unevenly such that the signal s₁(a) has an associated power level greater than a power level associated with the signal s₁(b); and a multiplier for phase sweeping the signal s₁(b) using a phase sweep frequency signal to produce a phase swept signal s₁(b).
 12. The base station of claim 11 further comprising: a first amplifier for amplifying the signal s₁(a) to produce an amplified signal s₁(a); and a second amplifier for amplifying the phase swept signal s₁(b) to produce an amplified phase swept signal s₁(b).
 13. The base station of claim 12, wherein power levels associated with the amplified signal s₁(a) and the amplified phase swept signal s₁(b) are approximately equal.
 14. The base station of claim 12, wherein the signal s₁(a) and phase swept signal s₁(b) are amplified an equal amount.
 15. The base station of claim 12, wherein the signal s₁(a) is amplified an amount greater than an amount phase swept signal s₁(b) is amplified.
 16. A base station comprising: a splitter for splitting a signal s₁ into signals s₁(a) and s₁(b), wherein the signal s₁ is split unevenly such that the signal s₁(a) has an associated power level greater than a power level associated with the signal s₁(b); and a multiplier for phase sweeping the signal s₁(a) using a phase sweep frequency signal to produce a phase swept signal s₁(b).
 17. The base station of claim 16 comprising the additional steps of: a first amplifier for amplifying the signal s₁(b) to produce an amplified signal s₁(b); and a second amplifier for amplifying the phase swept signal s₁(a) to produce an amplified phase swept signal s₁(a).
 18. The base station of claim 17, wherein power levels associated with the amplified signal s₁(b) and the amplified phase swept signal s₁(a) are approximately equal.
 19. The base station of claim 17, wherein the signal s₁(b) and phase swept signal s₁(a) are amplified an equal amount.
 20. The base station of claim 17, wherein the signal s₁(b) is amplified an amount greater than an amount phase swept signal s₁(a) is amplified. 